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LT6107 1 6107fa typical application features applications description high temperature high side current sense amp in sot-23 the lt ? 6107 is a versatile high side current sense ampli- ? er designed for operation over a wide temperature range. design ? exibility is provided by the excellent device char- acteristics: 250v maximum offset and 40na maximum input bias current. gain for each device is set by two re- sistors and allows for accuracy better than 1%. the LT6107 monitors current via the voltage across an external sense resistor (shunt resistor). internal circuitry converts input voltage to output current, allowing for a small sense signal on a high common mode voltage to be translated into a ground referenced signal. the low dc offset allows for monitoring very small sense voltages. as a result, a small valued shunt resistor can be used, which minimizes the power loss in the shunt. the wide 2.7v to 44v input voltage range, high accuracy and wide operating temperature range make the LT6107 ideal for automotive, industrial and power management applications. the very low power supply current of the LT6107 also makes it suitable for low power and battery operated applications. for applications not requiring the wide temperature range, see the lt6106. fully tested at C55c, 25c and 150c gain con? gurable with two resistors low offset voltage: 250v maximum output current: 1ma maximum supply range: 2.7v to 36v, 44v absolute maximum low input bias current: 40na maximum psrr: 106db minimum low supply current: 65a typical, v + = 12v low pro? le (1mm) thinsot tm package current shunt measurement battery monitoring power management motor control lamp monitoring overcurrent and fault detection LT6107 1k v out 200mv/a 6107 ta01a 100 3v to 36v load 0.02 C + v + v C out Cin +in 3v to 36v, 5a current sense with a v = 10 , lt, ltc and ltm are registered trademarks of linear technology corporation. thinsot is a trademark of linear technology corporation. all other trademarks are the property of their respective owners. measurement accuracy vs load current load current (a) 0 C1.2 accuracy (% of full scale) C1.0 C0.6 C0.4 C0.2 2 4 5 0.6 6107 ta01b C0.8 13 0 0.2 0.4 typical part, t a = 25c 5a full scale r sense = 0.02 a v = 10 r in = 100 r out = 1k v + = 3v
LT6107 2 6107fa pin configuration absolute maximum ratings supply voltage (v + to v ? )..........................................44v input voltage (+in to v ? ) ............................................ v + (?in to v ? ) ............................................ v + input current ........................................................?10ma output short-circuit duration .......................... inde? nite operating temperature range (note 2) ............................................. ?55c to 150c speci? ed temperature range (note 2) ............................................. ?55c to 150c storage temperature range ................... ?65c to 150c lead temperature (soldering, 10 sec) .................. 300c (note 1) out 1 v ? 2 top view s5 package 5-lead plastic tsot-23 ?in 3 5 v + 4 +in t jmax = 150c,
LT6107 3 6107fa note 1: stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. exposure to any absolute maximum rating condition for extended periods may affect device reliability and lifetime. in addition to the absolute maximum ratings, the output current of the LT6107 must be limited to insure that the power dissipation in the LT6107 does not allow the die temperature to exceed 150c. see the applications information section power dissipation considerations for further information. note 2: junction temperatures greater than 125c will promote accelerated aging. the LT6107 has demonstrated typical life beyond 1000 hours at 150c. electrical characteristics the denotes the speci? cations which apply over the full speci? ed operating temperature range, otherwise speci? cations are at t a = 25c. v + = 12v, v + = v sense + , r in = 100, r out = 10k, gain = 100 unless otherwise noted. (note 6) symbol parameter conditions min typ max units minimum output voltage (note 5) v sense = 0mv, r in = 100, r out = 10k 12 45 85 mv mv v sense = 0mv, r in = 500, r out = 10k, v + = 12v, 36v 716 40 mv mv bw signal bandwidth (C3db) i out = 1ma, r in = 100, r out = 5k 200 khz t r input step response (to 50% of output step) v sense = 100mv step, r in = 100, r out = 5k, rising edge 3.5 s i s supply current v + = 2.7v, i out = 0a, (v sense = C5mv) 60 85 120 a v + = 12v, i out = 0a, (v sense = C5mv) 65 95 125 a v + = 36v, i out = 0a, (v sense = C5mv) 70 100 135 a note 3: guaranteed by the gain error test. note 4: gain error refers to the contribution of the LT6107 internal circuitry and does not include errors in the external gain setting resistors. note 5: the LT6107 output is an open collector current source. the minimum output voltage scales directly with the ratio r out /10k. note 6: v sense + is the voltage at the high side of the sense resistor, r sense . see figure 1. note 7: v sense(max) is the maximum sense voltage for which the electrical characteristics will apply. higher voltages can affect performance but will not damage the part provided that the output current of the LT6107 does not exceed the allowable power dissipation as described in note 1. typical performance characteristics input offset voltage vs temperature input offset voltage (v) C200 percent of units (%) 10 12 16 120 6107 g23 4 8 14 6 2 0 C120 C40 0 40 200 v + = 12v v sense = 5mv r in = 100 r out = 10k 1068 units v os distribution supply voltage (v) 0 change in input offset voltage (v) 10 40 50 40 6107 g02 0 C10 C70 10 20 30 5 15 25 35 C30 70 60 30 20 C20 C40 C50 C60 v sense = 5mv r in = 100 r out = 10k typical units input offset voltage vs supply voltage temperature (c) C55 C35 C15 5 25 45 65 85 105 125 145 165 C300 C400 input offset voltage (v) C200 0 100 200 600 6107 g03 C100 300 400 500 v sense = 5mv v + = 12v r in = 100 r out = 10k a v = 100 typical units
LT6107 4 6107fa typical performance characteristics gain vs frequency step response 0mv to 10mv (r in = 100) step response 10mv to 20mv (r in = 100) gain vs frequency input bias current vs supply voltage power supply rejection ratio vs frequency 0 20 40 60 80 100 120 140 160 180 200 220 240 260 280 300 supply voltage (v) 0 input bias current (na) 40 6107 g05 10 5 20 15 30 35 45 25 50 v sense = 5mv r in = 100 t a = C55c t a = C40c t a = 25c t a = 70c t a = 125c t a = 150c t a = 175c frequency (hz) 20 power supply rejection ratio (db) 40 60 80 100 100 10k 100k 1m 6107 g06 0 1k 120 10 30 50 70 90 110 v out = 2.5v v out = 5v v out = 10v v + = 12.5v a v = 20 r in = 500 r out = 10k power supply rejection ratio vs frequency frequency (hz) 20 power supply rejection ratio (db) 40 60 80 100 100 10k 100k 1m 6107 g08 0 1k 120 10 30 50 70 90 110 v out = 0.5v v out = 1v v out = 2v v + = 12.5v a v = 20 r in = 100 r out = 2k frequency (hz) 10 gain (db) 40 45 5 0 35 20 30 25 15 1k 100k 1m 10m 6107 g09 C30 C25 C20 C15 C10 C5 10k v + = 12.5v a v = 100 r in = 100 r out = 10k v out = 10v v out = 2.5v v sense 20mv/div v out 500mv/div 0v 5s/div a v = 100 v out = 0v to 1v r out = 10k v + = 12v 6107 g10 v sense 20mv/div v out 500mv/div 0v 5s/div a v = 100 v out = 1v to 2v r out = 10k v + = 12v 6107 g11 frequency (hz) 10 gain (db) 40 45 5 0 35 20 30 25 15 1k 100k 1m 10m 6107 g14 C30 C25 C20 C15 C10 C5 10k v + = 12.5v a v = 20 r in = 500 r out = 10k v out = 10v v out = 2.5v gain error vs temperature gain error distribution gain error (%) C0.60 0 percent of units (%) 4 2 8 6 10 24 20 C0.48 C0.36 22 18 16 14 12 C0.24 C0.12 0 6107 g24 v + = 12.5v v sense = 500mv r in = 500 r out = 10k 11,072 units t a = 25c temperature (c) C60 gain error (%) C0.20 C0.10 120 140 180 160 6107 g04 C0.30 C0.40 C0.45 0 40 80 C40 C20 20 60 100 0.00 C0.25 C0.15 C0.35 C0.05 v out = 1v i out = 1ma r out = 1k v + = 36v v + = 12v v + = 5v v + = 2.7v
LT6107 5 6107fa output voltage swing vs temperature step response 0mv to 100mv (r in = 100) typical performance characteristics step response 0mv to 50mv (r in = 500) step response 50mv to 500mv (r in = 500) output voltage vs input sense voltage (0mv v sense 10mv) step response 10mv to 100mv (r in = 100) step response 50mv to 100mv (r in = 500) C60 C20 0 40 80 160 180 140 C40 20 60 120 10 0 temperature (c) output voltage (v) 11.00 11.05 11.15 11.10 6107 g07 10.95 10.90 10.85 10.80 v + = 12v a v = 100 r in = 100 r out = 10k v sense = 120mv v sense 200mv/div v out 2v/div 0v 5 + s/div a v = 100 v out = 0v to 10v r out = 10k v + = 12v 6107 g12 v sense 200mv/div v out 2v/div 0v 5s/div a v = 100 v out = 1v to 10v r out = 10k v + = 12v 6107 g13 v sense 100mv/div v out 500mv/div 0v 5s/div a v = 20 v out = 1v to 2v r out = 10k v + = 12v 6107 g15 v sense 100mv/div v out 500mv/div 0v 5s/div a v = 20 v out = 0v to 1v r out = 10k v + = 12v 6107 g16 v sense 1v/div v out 2v/div 0v 5s/div a v = 20 v out = 1v to 10v r out = 10k v + = 12v 6107 g17 step response 0mv to 500mv (r in = 500) v sense 1v/div v out 2v/div 0v 5s/div a v = 20 v out = 0v to 10v r out = 10k v + = 12v 6107 g18 v sense (mv) 0 v out (mv) 600 800 1100 1000 89 6107 g19 400 200 500 700 900 300 100 0 2 4 6 1 3 5 7 10 v + = 12v a v = 100 r in = 100 r out = 10k output voltage vs input sense voltage (0mv v sense 10mv) v sense (mv) 0 v out (mv) 120 160 220 200 89 6107 g20 80 40 100 140 180 60 20 0 2 4 6 1 3 5 7 10 v + = 12v a v = 20 r in = 500 r out = 10k
LT6107 6 6107fa block diagram pin functions out (pin 1): current output. out will source a current that is proportional to the sense voltage into an external resistor. v C (pin 2): normally connected to ground. Cin (pin 3): the internal sense ampli? er will drive Cin to the same potential as +in. a resistor (r in ) tied from v + to Cin sets the output current i out = v sense /r in . v sense is the voltage developed across r sense . +in (pin 4): must be tied to the system load end of the sense resistor, either directly or through a resistor. v + (pin 5): positive supply pin. the v + pin should be con- nected directly to either side of the sense resistor, r sense . supply current is drawn through this pin. the circuit may be con? gured so that the LT6107 supply current is or is not monitored along with the system load current. to monitor only the system load current, connect v + to the more positive side of the sense resistor. to monitor the total current, including that of the LT6107, connect v + to the more negative side of the sense resistor. C + v + v C out 6107 f01 v battery i out v sense r sense i load r out C + l o a d v out = v sense ? r out r in 14k 14k Cin +in 5 2 1 3 4 r in figure 1. LT6107 block diagram and typical connection typical performance characteristics v sense (mv) 0 v out (v) 4 8 12 2 6 10 40 80 120 160 6107 g21 200 20 0 60 100 140 180 v + = 12v a v = 100 r in = 100 r out = 10k v sense (mv) 0 v out (v) 4 8 12 2 6 10 200 400 600 800 6107 g22 1000 100 0 300 500 700 900 v + = 12v a v = 20 r in = 500 r out = 10k supply current vs supply voltage supply voltage (v) 0 0 supply current (a) 20 60 80 100 10 20 25 45 6107 g01 40 515 30 35 40 120 t a = C55c t a = C40c t a = 25c t a = 70c t a = 125c t a = 150c t a = 175c output voltage vs input sense voltage (0mv v sense 1v) output voltage vs input sense voltage (0mv v sense 200mv)
LT6107 7 6107fa applications information introduction the LT6107 high side current sense ampli? er (figure 1) pro- vides accurate monitoring of current through a user-selected sense resistor. the sense voltage is ampli? ed by a user- selected gain and level shifted from the positive power sup- ply to a ground-referred output. the output signal is analog and may be used as is, or processed with an output ? lter. theory of operation an internal sense ampli? er loop forces Cin to have the same potential as +in. connecting an external resistor, r in , between Cin and v + forces a potential across r in that is the same as the sense voltage across r sense . a corresponding current, v sense /r in , will ? ow through r in . the high impedance inputs of the sense ampli? er will not conduct this current, so it will ? ow through an internal pnp to the output pin as i out . the output current can be transformed into a voltage by adding a resistor from out to v C . the output voltage is then v o = v C + i out ? r out . table 1. useful gain con? gurations gain r in r out v sense at v out = 5v i out at v out = 5v 20 499 10k 250mv 500a 50 200 10k 100mv 500a 100 100 10k 50mv 500a gain r in r out v sense at v out = i out at v out = 2.5v 20 249 5k 125mv 500a 50 100 5k 50mv 500a 100 50 5k 25mv 500a selection of external current sense resistor the external sense resistor, r sense , has a signi? cant ef- fect on the function of a current sensing system and must be chosen with care. first, the power dissipation in the resistor should be con- sidered. the system load current will cause both heat and voltage loss in r sense . as a result, the sense resistor should be as small as possible while still providing the input dynamic range required by the measurement. note that input dynamic range is the difference between the maximum input signal and the minimum accurately mea- sured signal, and is limited primarily by input dc offset of the internal ampli? er of the LT6107. in addition, r sense must be small enough that v sense does not exceed the maximum input voltage speci? ed by the LT6107, even un- der peak load conditions. as an example, an application may require that the maximum sense voltage be 100mv. if this application is expected to draw 2a at peak load, r sense should be no more than 50m. once the maximum r sense value is determined, the mini- mum sense resistor value will be set by the resolution or dynamic range required. the minimum signal that can be accurately represented by this sense ampli? er is limited by the input offset. as an example, the LT6107 has a typical input offset of 150v. if the minimum current is 20ma, a sense resistor of 7.5m will set v sense to 150v. this is the same value as the input offset. a larger sense resis- tor will reduce the error due to offset by increasing the sense voltage for a given load current. choosing a 50m r sense will maximize the dynamic range and provide a system that has 100mv across the sense resistor at peak load (2a), while input offset causes an error equivalent to only 3ma of load current. peak dissipation is 200mw. if a 5m sense resistor is employed, then the effective current error is 30ma, while the peak sense voltage is reduced to 10mv at 2a, dissipating only 20mw. the low offset and corresponding large dynamic range of the LT6107 make it more ? exible than other solutions in this respect. the 150v typical offset gives 60db of dy- namic range for a sense voltage that is limited to 150mv maximum, and over 70db of dynamic range if the rated input maximum of 0.5v is allowed. sense resistor connection kelvin connection of the Cin and +in inputs to the sense resistor should be used in all but the lowest power appli- cations. solder connections and pc board interconnec- tions that carry high current can cause signi? cant error in measurement due to their relatively large resistances. one 10mm 10mm square trace of one-ounce copper is approximately 0.5m. a 1mv error can be caused by as little as 2a ? owing through this small interconnect. this will cause a 1% error in a 100mv signal. a 10a load cur- rent in the same interconnect will cause a 5% error for the same 100mv signal. by isolating the sense traces from the high current paths, this error can be reduced
LT6107 8 6107fa applications information by orders of magnitude. a sense resistor with integrated kelvin sense terminals will give the best results. figure 2 illustrates the recommended method. this approach can be helpful in cases where occasional bursts of high currents can be ignored. care should be taken when designing the board layout for r in , especially for small r in values. all trace and inter- connect resistances will increase the effective r in value, causing a gain error. selection of external output resistor, r out the output resistor, r out , determines how the output cur- rent is converted to voltage. v out is simply i out ? r out . in choosing an output resistor, the maximum output volt- age must ? rst be considered. if the following circuit is a buffer or adc with limited input range, then r out must be chosen so that i out(max) ? r out is less than the allowed maximum input range of this circuit. in addition, the output impedance is determined by r out . if the circuit to be driven has high enough input impedance, then almost any useful output impedance will be accept- able. however, if the driven circuit has relatively low input impedance, or draws spikes of current such as an adc might do, then a lower r out value may be required in order to preserve the accuracy of the output. as an example, if the input impedance of the driven circuit is 100 times r out , then the accuracy of v out will be reduced by 1% since: vi rr rr out out out in driven out in driven = + = ? ? () () i ir ir out out out out ?? .?? 100 101 099 = error sources the current sense system uses an ampli? er and resistors to apply gain and level shift the result. the output is then dependent on the characteristics of the ampli? er, such as gain and input offset, as well as resistor matching. ideally, the circuit output is: vv r r vri out sense out in sense sense sense == ?; ? in this case, the only error is due to resistor mismatch, which provides an error in gain only. however, offset volt- age and bias current cause additional errors. figure 3. shunt diode limits maximum input voltage to allow better low input resolution without overranging figure 2. kelvin input connection preserves accuracy with large load currents selection of external input resistor, r in r in should be chosen to allow the required resolution while limiting the output current to 1ma. in addition, the maximum value for r in is 500. by setting r in such that the largest expected sense voltage gives i out = 1ma, then the maximum output dynamic range is available. output dynamic range is limited by both the maximum allowed output current and the maximum allowed output voltage, as well as the minimum practical output signal. if less dynamic range is required, then r in can be increased accordingly, reducing the maximum output current and power dissipation. if low sense currents must be resolved accurately in a system that has a very wide dynamic range, a smaller r in than the maximum current spec allows may be used if the maximum current is limited in another way, such as with a schottky diode across r sense (figure 3). this will reduce the high current measurement accuracy by limiting the result, while increasing the low current measurement resolution. LT6107 r out v out 6107 f02 r in v + load r sense C + v + v C out Cin +in v + load d sense 6107 f03 r sense
LT6107 9 6107fa applications information output error due to the ampli? er dc offset voltage, v os ev r r out vos os out in () ? = the dc offset voltage of the ampli? er adds directly to the value of the sense voltage, v sense . this is the dominant error of the system and it limits the low end of the dynamic range. the paragraph selection of external current sense resistor provides details. output error due to the bias currents, i b + and i b C the bias current i b + ? ows into the positive input of the internal op amp. i b C ? ows into the negative input. e out(ibias) = r out i b + ? r sense r i n Ci b C assuming i b + i b C = i bias , and r sense << r in then: e out(ibias) Cr out ? i bias it is convenient to refer the error to the input: e in(ibias) Cr in ? i bias for instance if i bias is 60na and r in is 1k, the input referred error is 60v. note that in applications where r sense r in , i b + causes a voltage offset in r sense that cancels the er- ror due to i b C and e out(ibias) 0mv. in most applications, r sense << r in , the bias current error can be similarly re- duced if an external resistor r in + = (r in C r sense ) is con- nected as shown in figure 4. under both conditions: e in(ibias) = r in ? i os ; where i os = i b + C i b C if the offset current, i os , of the LT6107 ampli? er is 6na, the 60v error above is reduced to 6v. adding r in + as described will maximize the dynamic range of the circuit. for less sensitive designs, r in + is not necessary. output error due to gain error the LT6107 exhibits a typical gain error of C0.25% at 1ma output current. the primary source of gain error is due to the ? nite gain to the pnp output transistor, which results in a small percentage of the current in r in not appearing in the output load r out . minimum output voltage the curves of the output voltage vs input sense voltage show the behavior of the LT6107 with low input sense volt- ages. when v sense = 0v, the output voltage will always be slightly positive, the result of input offset voltages and of a small amount of quiescent current (0.7a to 1.2a) ? owing through the output device. the minimum output voltage in the electrical characteristics table include both these effects. power dissipation considerations the power dissipated by the LT6107 will cause a small increase in the die temperature. this rise in junction tem- perature can be calculated if the output current and the supply current are known. the power dissipated in the LT6107 due to the output signal is: p out = (v Cin C v out ) ? i out since v Cin v + , p out (v + C v out ) ? i out the power dissipated due to the quiescent supply current is: p q = i s ? (v + C v C ) the total power dissipated is the output dissipation plus the quiescent dissipation: p total = p out + p q the junction temperature is given by: t j = t a + e ja ? p total at the maximum operating supply voltage of 36v and the maximum guaranteed output current of 1ma, the total figure 4. second input r minimizes error due to input bias current LT6107 r out v out 6107 f04 r in C r in + v + load r sense C + v + v C out r in + = r in C C r sense Cin +in
LT6107 10 6107fa applications information power dissipation is 41mw. this amount of power dis- sipation will result in a 10c rise in junction temperature above the ambient temperature. it is important to note that the LT6107 has been designed to provide at least 1ma to the output when required, and can deliver more depending on the conditions. care must be taken to limit the maximum output current by proper choice of sense resistor and r in C and, if input fault con- ditions exist, external clamps. output filtering the output voltage, v out , is simply i out ? z out . this makes ? ltering straightforward. any circuit may be used which generates the required z out to get the desired ? lter response. for example, a capacitor in parallel with r out will give a lowpass response. this will reduce unwanted noise from the output, and may also be useful as a charge reservoir to keep the output steady while driving a switch- ing circuit such as a mux or adc. this output capacitor in parallel with an output resistor will create a pole in the output response at: f rc db out out C ?? ? 3 1 2 = / useful equations input voltage: v sense = ir voltage sense sense ? g gain: v out v r r sense out in = current gain: i transcond out i r r sense sense in = u uctance: i transimpedance: v out o vr sense in = 1 u ut i r r r sense sense out in = ? power supply connection for normal operation, the v + pin should be connected to either side of the sense resistor. either connection will meet the constraint that +in v + and Cin v + . during normal operation, v sense should not exceed 500mv (see v sense(max) under electrical characteristics). this ad- ditional constraint can be stated as v + C (+in) 500mv. referring to figure 5, feedback will force the voltages at the inputs Cin and +in to be equal to (v s C v sense ). connecting v + to the load side of the shunt results in equal voltages at +in, Cin and v + . connecting v + to the supply end of the shunt results in the voltages at +in and Cin to be v sense below v + . if the v + pin is connected to the supply side of the shunt resistor, the supply current drawn by the LT6107 is not included in the monitored current. if the v + pin is con- nected to the load side of the shunt resistor (figure 5), the supply current drawn by the LT6107 is included in the monitored current. it should be noted that in either con? guration, the output current of the LT6107 will not be monitored since it is drawn through the r in resistor connected to the positive side of the shunt. contact the factory for operation of the LT6107 with a v + outside of the recommended operating range. figure 5. LT6107 supply current monitored with the load reverse supply protection some applications may be tested with reverse-polarity supplies due to an expectation of the type of fault during operation. the LT6107 is not protected internally from ex- ternal reversal of supply polarity. to prevent damage that may occur during this condition, a schottky diode should be added in series with v C (figure 6). this will limit the reverse current through the LT6107. note that this diode will limit the low voltage performance of the LT6107 by ef- fectively reducing the supply voltage to the part by v d . LT6107 r out v out 6107 f05 r in v s load r sense C + v + v C out Cin +in
LT6107 11 6107fa information furnished by linear technology corpor ation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no representa- t i o n t h a t t h e i n t e r c o n n e c t i o n o f i t s c i r c u i t s a s d e s c r i b e d h e r e i n w i l l n o t i n f r i n g e o n e x i s t i n g p a t e n t r i g h t s . package description applications information in addition, if the output of the LT6107 is wired to a de- vice that will effectively short it to high voltage (such as through an esd protection clamp) during a reverse sup- ply condition, the LT6107s output should be connected through a resistor or schottky diode (figure 7). demo board demo board dc1240 is available for evaluation of the LT6107. response time the photos in the typical performance characteristics show the response of the LT6107 to a variety of input conditions and values of r in . the photos show that if the output cur- rent is very low or zero and an input transient occurs, there will be an increased delay before the output voltage begins changing while internal nodes are being charged. figure 6. schottky diode prevents damage during supply reversal figure 7. additional resistor r3 protects output during supply reversal s5 package 5-lead plastic tsot-23 (reference ltc dwg # 05-08-1635) 1.50 C 1.75 (note 4) 2. 8 0 bsc 0.30 C 0.45 typ 5 plcs (note 3) datum a 0.09 C 0.20 (note 3) s5 tsot-23 0302 rev b pin one 2.90 bsc (note 4) 0.95 bsc 1.90 bsc 0. 8 0 C 0.90 1.00 max 0.01 C 0.10 0.20 bsc 0.30 C 0.50 ref note: 1. dimensions are in millimeters 2. drawing not to scale 3. dimensions are inclusive of plating 4. dimensions are exclusive of mold flash and metal burr 5. mold flash shall not exceed 0.254mm 6. jedec package reference is mo-193 3. 8 5 max 0.62 max 0.95 ref recommended solder pad layout per ipc calculator 1.4 min 2.62 ref 1.22 ref 6107 f06 LT6107 r2 4.99k d1 v batt r sense l o a d v + v C out Cin +in C + r1 100 6107 f07 lt 6 1 0 7 r2 4.99k d1 v batt r3 1k r sense l o a d v + v C out Cin +in adc r1 100 C +
LT6107 12 6107fa linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax: (408) 434-0507 www.linear.com ? linear technology corporation 2008 lt 0608 rev a ? printed in usa related parts part number description comments lt1787 precision bidirectional, high side current sense ampli? er 75v v os , 60v, 60a operation lt6100 gain-selectable high side current sense ampli? er 4.1v to 48v, pin-selectable gain: 10, 12.5, 20, 25, 40, 50v/v ltc ? 6101/ltc6101hv high voltage, high side, precision current sense ampli? ers 4v to 60v/5v to 100v, gain con? gurable, sot-23 ltc6102/ltc6102hv zero drift high side current sense ampli? er 4v to 60v/5v to 100v operation, 10v offset, 1s step response, msop8/dfn ltc6103 dual high side, precision current sense ampli? er 4v to 60v, gain con? gurable 8-pin msop ltc6104 bidirectional high side, precision current sense ampli? er 4v to 60v, gain con? gurable 8-pin msop lt6105 rail-to-rail input precision high side current sense ampli? er C0.3v to 44v input common mode range, 300v offset, 1% gain accuracy, gain con? gurable lt6106 low cost, high side precision current sense ampli? er 2.7v to 36v, gain con? gurable, sot-23 typical application simple 400v current monitor 6107 ta02 LT6107 r in 100 v out r out 4.99k l o a d C + v out = ? v sense = 49.9 v sense r out r in m1 and m2 are fqd3p50 m1 2m 12v cmpz12l m2 400v bat46 v sense r sense i sense +C danger! lethal potentials present use caution danger!! high voltage!! v + v C out Cin +in

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